| 1 |
\chap Trial design
|
1 |
\chap Trial design
|
| 2 |
|
2 |
|
| 3 |
The whole design of radioastronomy receiver digitalization unit is constructed to be used in a wide range of applications and tasks related to digitalization of signal from radioastronomy receivers. A good illustrating problem for its use is a signal digitalisation from multiple antenna arrays.
|
3 |
The whole design of radioastronomy receiver digitalization unit is constructed to be used in a wide range of applications and tasks related to digitalization of signal from radioastronomy receivers. A good illustrating problem for its use is a signal digitalisation from multiple antenna arrays.
|
| 4 |
|
4 |
|
| 5 |
\sec Required parameters
|
5 |
\sec Required parameters
|
| 6 |
|
6 |
|
| 7 |
We require following technical parameter, to supersede existing digitalization units solutions.
|
7 |
We require following technical parameter, to supersede existing digitalization units solutions.
|
| 8 |
Primarily, we need wide dynamical range and high IP3. The receiver must accept wide dynamic signals because a typical radioastronomical signal has a form of a weak signal covered by a strong man-made noise or other undesired noises as lighting, Sun emissions etc.
|
8 |
Primarily, we need wide dynamical range and high IP3. The receiver must accept wide dynamic signals because a typical radioastronomical signal has a form of a weak signal covered by a strong man-made noise or other undesired noises as lighting, Sun emissions etc.
|
| 9 |
|
9 |
|
| 10 |
Summary of other additional required parameters follows
|
10 |
Summary of other additional required parameters follows
|
| 11 |
|
11 |
|
| 12 |
\begitems
|
12 |
\begitems
|
| 13 |
* Dynamical range better than 80 dB see section \ref[dynamic-range-theory] for explanation
|
13 |
* Dynamical range better than 80 dB see section \ref[dynamic-range-theory] for explanation
|
| 14 |
* Phase stability between channels
|
14 |
* Phase stability between channels
|
| 15 |
* Low noise (all types)
|
15 |
* Low noise (all types)
|
| 16 |
* Sampling jitter better than 100 metres
|
16 |
* Sampling jitter better than 100 metres
|
| 17 |
* Support for any number of receivers in range 1 to 8
|
17 |
* Support for any number of receivers in range 1 to 8
|
| 18 |
\enditems
|
18 |
\enditems
|
| 19 |
|
19 |
|
| 20 |
Now we analyzes several parameters more precisely.
|
20 |
Now we analyzes several parameters more precisely.
|
| 21 |
|
21 |
|
| 22 |
\sec Sampling frequency
|
22 |
\sec Sampling frequency
|
| 23 |
|
23 |
|
| 24 |
Sampling frequency is not limited by the technical constrains in the trial design. This parameter is especially limited by the sampling frequencies of analog-to-digital conversion chips available on the market and interface bandwidth. Combination of the required parameters -- dynamic range requiring at least 16bit and a minimum sampling frequency of 1$\ $MSPS leads to need of high end ADC chips which does not support such low sampling frequencies at all. Their minimum sampling frequency is 5$\ $MSPS.
|
24 |
Sampling frequency is not limited by the technical constrains in the trial design. This parameter is especially limited by the sampling frequencies of analog-to-digital conversion chips available on the market and interface bandwidth. Combination of the required parameters -- dynamic range requiring at least 16bit and a minimum sampling frequency of 1$\ $MSPS leads to need of high end ADC chips which does not support such low sampling frequencies at all. Their minimum sampling frequency is 5$\ $MSPS.
|
| 25 |
|
25 |
|
| 26 |
We calculate minimum data bandwidth data rate for eight receivers, 2 bytes per sample and 5$\ $MSPS as $8 \cdot 2 \cdot 5\cdot 10^6 = 80\ $MB/s. Such data rate is at the limit of real writing speed o classical HDD and it is almost double of real bandwidth of USB 2.0 interface. As result of this facts we must use faster interface. Faster interface is especially needed in case where we need faster sampling rates than ADC minimal 5$\ $MSPS sample rate.
|
26 |
We calculate minimum data bandwidth data rate for eight receivers, 2 bytes per sample and 5$\ $MSPS as $8 \cdot 2 \cdot 5\cdot 10^6 = 80\ $MB/s. Such data rate is at the limit of real writing speed o classical HDD and it is almost double of real bandwidth of USB 2.0 interface. As result of this facts we must use faster interface. Faster interface is especially needed in case where we need faster sampling rates than ADC minimal 5$\ $MSPS sample rate.
|
| 27 |
Most perspective interfaces for use in our type of application is USB 3.0 or PCI Express interface. Although USB 3.0 is new technology without availability of good development tools. We used PCI Express interface as simplest and most reliable solution.
|
27 |
Most perspective interfaces for use in our type of application is USB 3.0 or PCI Express interface. Although USB 3.0 is new technology without availability of good development tools. We used PCI Express interface as simplest and most reliable solution.
|
| 28 |
|
28 |
|
| 29 |
\sec System scalability
|
29 |
\sec System scalability
|
| 30 |
|
30 |
|
| 31 |
For analogue channels scalability, special parameters of ADC modules are required. Ideally, there should be a separate output for each analogue channel in ADC module. ADC module must also have separate outputs for frames and data output clocks. These parameters allow for conduction at relatively low digital data rates. As a result, the digital signal can be conducted even through long wires. Modular concept allows separation from central logic which support optimization of number analogue channels.
|
31 |
For analogue channels scalability, special parameters of ADC modules are required. Ideally, there should be a separate output for each analogue channel in ADC module. ADC module must also have separate outputs for frames and data output clocks. These parameters allow for conduction at relatively low digital data rates. As a result, the digital signal can be conducted even through long wires. Modular concept allows separation from central logic which support optimization of number analogue channels.
|
| 32 |
|
32 |
|
| 33 |
Clock and data signals will be then handled distinctively in our modular scalable design. Selected ADC chip are guaranteed to have defined clock skew between sampling and data output clock. This allows taking data and frame clocks from the first ADC module only. The rest of the data and frame clocks from other ADC modules can be measured for diagnostic purposes (failure detection, jitter measurement etc.) but these redundant signals are not used for data sampling. If more robustness is required in final application, DCO and FR signal may be collected from other modules and routed through an voting logic which will correct possible signal defects.
|
33 |
Clock and data signals will be then handled distinctively in our modular scalable design. Selected ADC chip are guaranteed to have defined clock skew between sampling and data output clock. This allows taking data and frame clocks from the first ADC module only. The rest of the data and frame clocks from other ADC modules can be measured for diagnostic purposes (failure detection, jitter measurement etc.) but these redundant signals are not used for data sampling. If more robustness is required in final application, DCO and FR signal may be collected from other modules and routed through an voting logic which will correct possible signal defects.
|
| 34 |
|
34 |
|
| 35 |
This system concept allows for scalability, that is technically limited by a number of differential signals on host side and its computational power. There is another advantage of scalable data acquisition system -- an economic one. Observatories or end users can make a choice of how much money are they willing to spent on radioastronomy receiver system. This freedom of choice is especially useful for science sites without previous experience in radioastronomy observations.
|
35 |
This system concept allows for scalability, that is technically limited by a number of differential signals on host side and its computational power. There is another advantage of scalable data acquisition system -- an economic one. Observatories or end users can make a choice of how much money are they willing to spent on radioastronomy receiver system. This freedom of choice is especially useful for science sites without previous experience in radioastronomy observations.
|
| 36 |
|
36 |
|
| 37 |
\secc Differential signaling
|
37 |
\secc Differential signaling
|
| 38 |
|
38 |
|
| 39 |
The above mentioned concept of scalable design requires relatively long circuit traces between ADC and digital unit which captures the data and performs the computations. The long distance between the digital processing unit and the analog-to-digital conversion unit has an advantage in noise retention typically produced by digital circuits. Those digital circuits, such as FPGA, Ethernet or other flip-flops blocks and circuit traces, usually work at high frequencies and emit wide-band noise with relatively low power. In such cases any increase in a distance between the noise source and analog signal source increase S/N significantly. However, at the same time a long distance brings problems with the digital signal transmission between ADC and computational unit. But this obstacle should be resolved more easily in free-space than on board routing. The high-quality differential signalling shielded cables should be used such as massively produced and cheap SATA cables. This technology has two advantages over PCB signal routing. First, it can use twisted pair of wires for leak inductance suppression in signal path and second, the twisted pair may additionally be shielded by uninterrupted metal foil.
|
39 |
The above mentioned concept of scalable design requires relatively long circuit traces between ADC and digital unit which captures the data and performs the computations. The long distance between the digital processing unit and the analog-to-digital conversion unit has an advantage in noise retention typically produced by digital circuits. Those digital circuits, such as FPGA, Ethernet or other flip-flops blocks and circuit traces, usually work at high frequencies and emit wide-band noise with relatively low power. In such cases any increase in a distance between the noise source and analog signal source increase S/N significantly. However, at the same time a long distance brings problems with the digital signal transmission between ADC and computational unit. But this obstacle should be resolved more easily in free-space than on board routing. The high-quality differential signalling shielded cables should be used such as massively produced and cheap SATA cables. This technology has two advantages over PCB signal routing. First, it can use twisted pair of wires for leak inductance suppression in signal path and second, the twisted pair may additionally be shielded by uninterrupted metal foil.
|
| 40 |
|
40 |
|
| 41 |
\secc Phase matching
|
41 |
\secc Phase matching
|
| 42 |
|
42 |
|
| 43 |
For multiple antenna radioastronomy projects, system phase stability is a mandatory condition. It allows precise high resolution imaging of objects, increases signal to noise ratios in several observation methods and allows use of advanced algorithms for signal processing.
|
43 |
For multiple antenna radioastronomy projects, system phase stability is a mandatory condition. It allows precise high resolution imaging of objects, increases signal to noise ratios in several observation methods and allows use of advanced algorithms for signal processing.
|
| 44 |
|
44 |
|
| 45 |
High phase stability in our scalable design is achieved through centralized frequency generation and distribution with multi-output LVPECL hubs (CLKHUB02A), that have equiphased outputs for multiple devices. LVPECL logic is used on every system critical clock signal distribution hub. LVPECL logic has advantage over LVDS in signal integrity robustness. LVPECL uses higher logical levels and higher signalling currents. Power consumption of LVPECL logic are near constant over operating frequency range due to use of bipolar transistors this minimizes voltage glitches which are typical for CMOS logic. One drawbacks of that parameters is high power consumption of LVPECL logic which easily reach tens of milliamperes per device.
|
45 |
High phase stability in our scalable design is achieved through centralized frequency generation and distribution with multi-output LVPECL hubs (CLKHUB02A), that have equiphased outputs for multiple devices. LVPECL logic is used on every system critical clock signal distribution hub. LVPECL logic has advantage over LVDS in signal integrity robustness. LVPECL uses higher logical levels and higher signalling currents. Power consumption of LVPECL logic are near constant over operating frequency range due to use of bipolar transistors this minimizes voltage glitches which are typical for CMOS logic. One drawbacks of that parameters is high power consumption of LVPECL logic which easily reach tens of milliamperes per device.
|
| 46 |
|
46 |
|
| 47 |
This design ensures that all system devices have access to the defined phase and known frequency.
|
47 |
This design ensures that all system devices have access to the defined phase and known frequency.
|
| 48 |
|
48 |
|
| 49 |
\sec System description
|
49 |
\sec System description
|
| 50 |
|
50 |
|
| 51 |
In this section testing system based on Xilinx ML605 development board \ref[ML605-development-board] will be described. This board was used in previous finished project and was unused until now, but FPGA parrameters are more than enough we need in fast data aquisition system.
|
51 |
In this section testing system based on Xilinx ML605 development board \ref[ML605-development-board] will be described. This board was used in previous finished project and was unused until now, but FPGA parrameters are more than enough we need in fast data aquisition system.
|
| 52 |
|
52 |
|
| 53 |
\secc Frequency synthesis
|
53 |
\secc Frequency synthesis
|
| 54 |
|
54 |
|
| 55 |
We have used a centralized topology as a basis for frequency synthesis. One precise high-frequency and low-jitter digital oscillator has been used \cite[MLAB-GPSDO], while other working frequencies have been derived from it by the division of its signal. This central oscillator has a software defined GPS disciplined control loop for frequency stabilization.\fnote{SDGPSDO design has been developed in parallel to this diploma thesis as a related project, but it is not explicitly required by the diploma thesis. Thus is described in separate document}
|
55 |
We have used a centralized topology as a basis for frequency synthesis. One precise high-frequency and low-jitter digital oscillator has been used \cite[MLAB-GPSDO], while other working frequencies have been derived from it by the division of its signal. This central oscillator has a software defined GPS disciplined control loop for frequency stabilization.\fnote{SDGPSDO design has been developed in parallel to this diploma thesis as a related project, but it is not explicitly required by the diploma thesis. Thus is described in separate document}
|
| 56 |
We have used new methods of software frequency monitoring and compensation in order to meet modern requirements on radioastronomy equipment which needs precise frequency and phase stability over a wide baseline scales for effective radioastronomy imaging.
|
56 |
We have used new methods of software frequency monitoring and compensation in order to meet modern requirements on radioastronomy equipment which needs precise frequency and phase stability over a wide baseline scales for effective radioastronomy imaging.
|
| 57 |
|
57 |
|
| 58 |
GPSDO device consists the Si570 chip with LVPECL output. Phase jitter of GPSDO is determined mainly by Si570 phase noise. Parameters of used Si570 from source \cite[si570-chip] are summarized in table \ref[LO-noise].
|
58 |
GPSDO device consists the Si570 chip with LVPECL output. Phase jitter of GPSDO is determined mainly by Si570 phase noise. Parameters of used Si570 from source \cite[si570-chip] are summarized in table \ref[LO-noise].
|
| 59 |
|
59 |
|
| 60 |
GPSDO design included in data acquisition system has special feature -- generates time marks for precise time-stamping of received signal. Timestamps are created by disabling of local oscillator outputs connected to SDRX01B receivers for 100 us. As result rectangle click in ADC input signal is created which appears as horizontal line in spectrogram.
|
60 |
GPSDO design included in data acquisition system has special feature -- generates time marks for precise time-stamping of received signal. Timestamps are created by disabling of local oscillator outputs connected to SDRX01B receivers for 100 us. As result rectangle click in ADC input signal is created which appears as horizontal line in spectrogram.
|
| 61 |
Timestamps should be seen in image \ref[meteor-reflection] (above and below meteor reflection).
|
61 |
Timestamps should be seen in image \ref[meteor-reflection] (above and below meteor reflection).
|
| 62 |
|
62 |
|
| 63 |
Time-marking should be improved in future by digitalization of GPS signal received by antenna on observational station. GPS signal can be then directly sampled by dedicated receiver and one separate ADC module. Datafile then consists samples from channels of radio-astronomy receivers along with GPS signal containing precise time information.
|
63 |
Time-marking should be improved in future by digitalization of GPS signal received by antenna on observational station. GPS signal can be then directly sampled by dedicated receiver and one separate ADC module. Datafile then consists samples from channels of radio-astronomy receivers along with GPS signal containing precise time information.
|
| 64 |
|
64 |
|
| 65 |
|
65 |
|
| 66 |
\midinsert \clabel[LO-noise]{Phase noise of used local oscillator}
|
66 |
\midinsert \clabel[LO-noise]{Phase noise of used local oscillator}
|
| 67 |
\ctable{lcc}{
|
67 |
\ctable{lcc}{
|
| 68 |
& \multispan2 \hfil Phase Noise [dBc/Hz] \hfil \cr
|
68 |
& \multispan2 \hfil Phase Noise [dBc/Hz] \hfil \cr
|
| 69 |
Offset Frequency & $F_{out}$ 156.25 MHz & $F_{out}$ 622.08 MHz \cr
|
69 |
Offset Frequency & $F_{out}$ 156.25 MHz & $F_{out}$ 622.08 MHz \cr
|
| 70 |
100 [Hz] & –105 & –97 \cr
|
70 |
100 [Hz] & –105 & –97 \cr
|
| 71 |
1 [kHz] & –122 & –107 \cr
|
71 |
1 [kHz] & –122 & –107 \cr
|
| 72 |
10 [kHz] & –128 & –116 \cr
|
72 |
10 [kHz] & –128 & –116 \cr
|
| 73 |
100 [kHz] & –135 & –121 \cr
|
73 |
100 [kHz] & –135 & –121 \cr
|
| 74 |
1 [MHz] & –144 & –134 \cr
|
74 |
1 [MHz] & –144 & –134 \cr
|
| 75 |
10 [MHz] & –147 & –146 \cr
|
75 |
10 [MHz] & –147 & –146 \cr
|
| 76 |
100 [MHz] & n/a & –148 \cr
|
76 |
100 [MHz] & n/a & –148 \cr
|
| 77 |
}
|
77 |
}
|
| 78 |
\caption/t Phase noise of used Silicon Laboratories Si570 chip. Offset frequency is measured from carrier frequency. Values are tabled for two district carrier frequencies.
|
78 |
\caption/t Phase noise of used Silicon Laboratories Si570 chip. Offset frequency is measured from carrier frequency. Values are tabled for two district carrier frequencies.
|
| 79 |
\endinsert
|
79 |
\endinsert
|
| 80 |
|
80 |
|
| 81 |
Every ADC module will be directly connected to CLKHUB02A module which takes sampling clock signal delivered by FPGA from main local oscillator. This signal should use high quality differential signaling cable -- we should use SATA cable for this purpose. FPGA may slightly affect clock signal quality by additive noise, but has negligible effect in application where developed system will be used.
|
81 |
Every ADC module will be directly connected to CLKHUB02A module which takes sampling clock signal delivered by FPGA from main local oscillator. This signal should use high quality differential signaling cable -- we should use SATA cable for this purpose. FPGA may slightly affect clock signal quality by additive noise, but has negligible effect in application where developed system will be used.
|
| 82 |
|
82 |
|
| 83 |
|
83 |
|
| 84 |
\secc Signal cable connectors
|
84 |
\secc Signal cable connectors
|
| 85 |
|
85 |
|
| 86 |
\label[signal-cables]
|
86 |
\label[signal-cables]
|
| 87 |
|
87 |
|
| 88 |
Several widely used and commercially easily accessible differential connectors were considered to be use in our design.
|
88 |
Several widely used and commercially easily accessible differential connectors were considered to be use in our design.
|
| 89 |
|
89 |
|
| 90 |
\begitems
|
90 |
\begitems
|
| 91 |
* HDMI % [[http://en.wikipedia.org/wiki/Hdmi|HDMI]]</del>
|
91 |
* HDMI % [[http://en.wikipedia.org/wiki/Hdmi|HDMI]]</del>
|
| 92 |
* SATA %{http://en.wikipedia.org/wiki/Serial_attached_SCSI#Connectors|SAS]]/[[http://en.wikipedia.org/wiki/Serial_ATA|SATA]]
|
92 |
* SATA %{http://en.wikipedia.org/wiki/Serial_attached_SCSI#Connectors|SAS]]/[[http://en.wikipedia.org/wiki/Serial_ATA|SATA]]
|
| 93 |
* DisplayPort %[[http://en.wikipedia.org/wiki/Display_port|DisplayPort]]</del>
|
93 |
* DisplayPort %[[http://en.wikipedia.org/wiki/Display_port|DisplayPort]]</del>
|
| 94 |
* SAS/miniSAS
|
94 |
* SAS/miniSAS
|
| 95 |
\enditems
|
95 |
\enditems
|
| 96 |
|
96 |
|
| 97 |
At the end, MiniSAS connector was chosen as the best option to be used in connecting together multiple ADC modules. A transition between SATA and miniSAS is achieved by SAS to SATA adapter cable which is commonly used in servers to connect SAS controller to multiple SATA hard disc in RAID systems and thus is commercially easily available. It is compatible with existing SATA cabling systems and aggregates multiple SATA cables to a single connector, it has SPI configuration lines which can be seen on the following picture \ref[img-miniSAS-cable] as standard pinheader connector.
|
97 |
At the end, MiniSAS connector was chosen as the best option to be used in connecting together multiple ADC modules. A transition between SATA and miniSAS is achieved by SAS to SATA adapter cable which is commonly used in servers to connect SAS controller to multiple SATA hard disc in RAID systems and thus is commercially easily available. It is compatible with existing SATA cabling systems and aggregates multiple SATA cables to a single connector, it has SPI configuration lines which can be seen on the following picture \ref[img-miniSAS-cable] as standard pinheader connector.
|
| 98 |
The main drawback of miniSAS PCB connectors lies in the fact, that they are manufactured in SMT versions only, SMT design may eventually decrease the durability of the connector even if outer metal housing of connector is designed to be mounted using a standard through-hole mounting method.
|
98 |
The main drawback of miniSAS PCB connectors lies in the fact, that they are manufactured in SMT versions only, SMT design may eventually decrease the durability of the connector even if outer metal housing of connector is designed to be mounted using a standard through-hole mounting method.
|
| 99 |
|
99 |
|
| 100 |
\midinsert
|
100 |
\midinsert
|
| 101 |
\clabel[img-miniSAS-cable]{Used miniSAS cable}
|
101 |
\clabel[img-miniSAS-cable]{Used miniSAS cable}
|
| 102 |
\picw=5cm \cinspic ./img/miniSAS_SATA_cable.jpg
|
102 |
\picw=5cm \cinspic ./img/miniSAS_SATA_cable.jpg
|
| 103 |
\caption/f An example of miniSAS cable similar to used.
|
103 |
\caption/f An example of miniSAS cable similar to used.
|
| 104 |
\endinsert
|
104 |
\endinsert
|
| 105 |
|
105 |
|
| 106 |
\secc Signal integrity requirements
|
106 |
\secc Signal integrity requirements
|
| 107 |
|
107 |
|
| 108 |
\label[diff-signaling]
|
108 |
\label[diff-signaling]
|
| 109 |
|
109 |
|
| 110 |
We use ADC devices that have DATA clock frequency eight times higher than sampling frequency in single line output mode, implying a 40 MHz output bit rate. This imply $ 1/4 \cdot 10^7 = 25\ $ns time length of data bit, which is equivalent to 7.5m light path in free space. If we use copper PCB with FR4 substrate layer or coaxial/twinax cable, we could obtain velocity factor of 0.66 at worst condition. Then the light path for the same bit rate $t_s$ will be 4.95 m. Although we do not have any cables in system with comparable lengths, worst data bit skew described by data sheets of used components is $0.3 \cdot t_s$, which is 1.485 m. Therefore length matching is not critical in our current design operated on lowest sampling speed. Length matching becomes critical in future version with higher sampling rates, then cable length must be matched. However SATA cabling technology is prepared for that case and matched SATA cables are standard merchandise.
|
110 |
We use ADC devices that have DATA clock frequency eight times higher than sampling frequency in single line output mode, implying a 40 MHz output bit rate. This imply $ 1/4 \cdot 10^7 = 25\ $ns time length of data bit, which is equivalent to 7.5m light path in free space. If we use copper PCB with FR4 substrate layer or coaxial/twinax cable, we could obtain velocity factor of 0.66 at worst condition. Then the light path for the same bit rate $t_s$ will be 4.95 m. Although we do not have any cables in system with comparable lengths, worst data bit skew described by data sheets of used components is $0.3 \cdot t_s$, which is 1.485 m. Therefore length matching is not critical in our current design operated on lowest sampling speed. Length matching becomes critical in future version with higher sampling rates, then cable length must be matched. However SATA cabling technology is prepared for that case and matched SATA cables are standard merchandise.
|
| 111 |
|
111 |
|
| 112 |
\secc ADC modules design
|
112 |
\secc ADC modules design
|
| 113 |
|
113 |
|
| 114 |
\midinsert
|
114 |
\midinsert
|
| 115 |
\clabel[adcdual-preview]{Preview of designed ADCdual PCB}
|
115 |
\clabel[adcdual-preview]{Preview of designed ADCdual PCB}
|
| 116 |
\picw=10cm \cinspic ./img/ADCdual_Top.png
|
116 |
\picw=10cm \cinspic ./img/ADCdual_Top.png
|
| 117 |
\picw=10cm \cinspic ./img/ADCdual_Bottom.png
|
117 |
\picw=10cm \cinspic ./img/ADCdual_Bottom.png
|
| 118 |
\caption/f Modelled previews of designed and realised PCB of ADCdual01A modules. Differential pairs routing are clearly visible.
|
118 |
\caption/f Modelled previews of designed and realised PCB of ADCdual01A modules. Differential pairs routing are clearly visible.
|
| 119 |
\endinsert
|
119 |
\endinsert
|
| 120 |
|
120 |
|
| 121 |
\secc ADC selection
|
121 |
\secc ADC selection
|
| 122 |
|
122 |
|
| 123 |
There exist several standard ADC signaling formats currently used in communication with FPGA.
|
123 |
There exist several standard ADC signaling formats currently used in communication with FPGA.
|
| 124 |
|
124 |
|
| 125 |
\begitems
|
125 |
\begitems
|
| 126 |
* DDR LVDS
|
126 |
* DDR LVDS
|
| 127 |
* JEDEC 204B
|
127 |
* JEDEC 204B
|
| 128 |
* JESD204A
|
128 |
* JESD204A
|
| 129 |
* Paralel LVDS
|
129 |
* Paralel LVDS
|
| 130 |
* Serdes
|
130 |
* Serdes
|
| 131 |
* serial LVDS
|
131 |
* serial LVDS
|
| 132 |
\enditems
|
132 |
\enditems
|
| 133 |
|
133 |
|
| 134 |
Because we need to use the smallest number of cables, the choice fell on the serial LVDS format. Small number of differential pairs is an important parameter determining the construction complexity and reliability\cite[serial-lvds]. No much many currently existing ADC devices have this kind of digital interface. An ultrasound AFE device chips seems to be ideal for this purpose -- the chip has integrated both front-end amplifiers and filters. It has a drawback though - it is incapable of handling differential input signal and has a relatively low dynamic range (as it consists only of 12bit ADC) and has many single ended ADC channels. Consequently scaling is possible only by a factor of 4 receivers (making 8 analogue single ended channels).
|
134 |
Because we need to use the smallest number of cables, the choice fell on the serial LVDS format. Small number of differential pairs is an important parameter determining the construction complexity and reliability\cite[serial-lvds]. No much many currently existing ADC devices have this kind of digital interface. An ultrasound AFE device chips seems to be ideal for this purpose -- the chip has integrated both front-end amplifiers and filters. It has a drawback though - it is incapable of handling differential input signal and has a relatively low dynamic range (as it consists only of 12bit ADC) and has many single ended ADC channels. Consequently scaling is possible only by a factor of 4 receivers (making 8 analogue single ended channels).
|
| 135 |
|
135 |
|
| 136 |
If we add a requirement of separate output for every analogue channel and a 16bit depth we find that there are only a few 2-Channel simultaneous sampling ADCs currently existing which meet these requirements. We have summarized those ADCs in the following table \ref[ADC-types]
|
136 |
If we add a requirement of separate output for every analogue channel and a 16bit depth we find that there are only a few 2-Channel simultaneous sampling ADCs currently existing which meet these requirements. We have summarized those ADCs in the following table \ref[ADC-types]
|
| 137 |
|
137 |
|
| 138 |
\midinsert
|
138 |
\midinsert
|
| 139 |
\typosize[9/11] \def\tabiteml{ }\let\tabitemr=\tabiteml
|
139 |
\typosize[9/11] \def\tabiteml{ }\let\tabitemr=\tabiteml
|
| 140 |
\clabel[ADC-types]{Available ADC types}
|
140 |
\clabel[ADC-types]{Available ADC types}
|
| 141 |
\ctable{lccccccc}{
|
141 |
\ctable{lccccccc}{
|
| 142 |
\hfil ADC Type & LTC2271 & LTC2190 & LTC2191 & LTC2192 & LTC2193 & LTC2194 & LTC2195 \cr
|
142 |
\hfil ADC Type & LTC2271 & LTC2190 & LTC2191 & LTC2192 & LTC2193 & LTC2194 & LTC2195 \cr
|
| 143 |
SNR [dB] & 84.1 & 77 & 77 & 77 & 76.8 & 76.8 & 76.8 \cr
|
143 |
SNR [dB] & 84.1 & 77 & 77 & 77 & 76.8 & 76.8 & 76.8 \cr
|
| 144 |
SFDR [dB] & 99 & 90 & 90 & 90 & 90 & 90 & 90 \cr
|
144 |
SFDR [dB] & 99 & 90 & 90 & 90 & 90 & 90 & 90 \cr
|
| 145 |
S/H Bandwidth [MHz] & 200 & \multispan6 550 \strut \cr
|
145 |
S/H Bandwidth [MHz] & 200 & \multispan6 550 \strut \cr
|
| 146 |
Sampling rate [MSPS] & 20 & 25 & 40 & 65 & 80 & 105 & 125 \cr
|
146 |
Sampling rate [MSPS] & 20 & 25 & 40 & 65 & 80 & 105 & 125 \cr
|
| 147 |
Configuration & \multispan7 SPI \strut \cr
|
147 |
Configuration & \multispan7 SPI \strut \cr
|
| 148 |
Package & \multispan7 \hfil 52-Lead (7mm $\times$ 8mm) QFN \hfil \strut \cr
|
148 |
Package & \multispan7 \hfil 52-Lead (7mm $\times$ 8mm) QFN \hfil \strut \cr
|
| 149 |
}
|
149 |
}
|
| 150 |
\caption/t The summary of available ADC types and theirs characteristics.
|
150 |
\caption/t The summary of available ADC types and theirs characteristics.
|
| 151 |
\endinsert
|
151 |
\endinsert
|
| 152 |
|
152 |
|
| 153 |
All parts in this category are compatible with one board layout. Main differences lay in the sampling frequency and signal to noise ratio, with the slowest having a maximum sampling frequency of 20 MHz. However all of them have a minimal sampling frequency of 5 MSPS and all are configurable over a serial interface (SPI). SPI seems to be a standard interface used in high-end ADC chips made by the largest manufacturers (Analog Devices, Linear technology, Texas instruments, Maxim integrated..). We selected two slowest types for our evaluation design. Then PCB for this part have been designed.
|
153 |
All parts in this category are compatible with one board layout. Main differences lay in the sampling frequency and signal to noise ratio, with the slowest having a maximum sampling frequency of 20 MHz. However all of them have a minimal sampling frequency of 5 MSPS and all are configurable over a serial interface (SPI). SPI seems to be a standard interface used in high-end ADC chips made by the largest manufacturers (Analog Devices, Linear technology, Texas instruments, Maxim integrated..). We selected two slowest types for our evaluation design. Then PCB for this part have been designed.
|
| 154 |
We decided that ADCdual01A modules have a standard MLAB construction layout with four mounting holes in corners aligned in defined raster of 400 mils.
|
154 |
We decided that ADCdual01A modules have a standard MLAB construction layout with four mounting holes in corners aligned in defined raster of 400 mils.
|
| 155 |
|
155 |
|
| 156 |
Data serial data outputs of ADC modules should be connected directly by LVDS signalling levels conducted by SATA cables to FPGAs for the basic primary signal processing. The ADC chips used in the modules has a selectable bit width of data output bus and thus the output SATA connectors have signals arranged to contain a single bit from every ADC channel. This creates a signal concept enabling a selection of a proper bus bit-width according to the sampling rate (higher bus bit-width downgrades signalling speed and vice versa.)
|
156 |
Data serial data outputs of ADC modules should be connected directly by LVDS signalling levels conducted by SATA cables to FPGAs for the basic primary signal processing. The ADC chips used in the modules has a selectable bit width of data output bus and thus the output SATA connectors have signals arranged to contain a single bit from every ADC channel. This creates a signal concept enabling a selection of a proper bus bit-width according to the sampling rate (higher bus bit-width downgrades signalling speed and vice versa.)
|
| 157 |
|
157 |
|
| 158 |
In order to connect the above mentioned signalling layout, miniSAS to multiple SATA cable should be used as described in section \ref[signal-cables].
|
158 |
In order to connect the above mentioned signalling layout, miniSAS to multiple SATA cable should be used as described in section \ref[signal-cables].
|
| 159 |
|
159 |
|
| 160 |
A KiCAD design suite had been chosen for PCB layout. However, the version is, despite having integrated CERN Push \& Shove routing capability, slightly unstable as it sometimes crushes due to an exception during routing. On the basis of these stability issues, the design had to be saved quite often. On the other hand, compared to commercially available solutions, such as MentorGraphics PADS or Cadence Orcad, the Open-source KiCAD provides an acceptable option and it easily surpasses a widely used Eagle software.
|
160 |
A KiCAD design suite had been chosen for PCB layout. However, the version is, despite having integrated CERN Push \& Shove routing capability, slightly unstable as it sometimes crushes due to an exception during routing. On the basis of these stability issues, the design had to be saved quite often. On the other hand, compared to commercially available solutions, such as MentorGraphics PADS or Cadence Orcad, the Open-source KiCAD provides an acceptable option and it easily surpasses a widely used Eagle software.
|
| 161 |
|
161 |
|
| 162 |
As a part of work on the thesis, new PCB footprints for FMC, SATA, ADCs a and miniSAS connectors have been designed and were committed to KiCAD github library repository. They are now publicly available on the official KiCAD repository at GitHub.
|
162 |
As a part of work on the thesis, new PCB footprints for FMC, SATA, ADCs a and miniSAS connectors have been designed and were committed to KiCAD github library repository. They are now publicly available on the official KiCAD repository at GitHub.
|
| 163 |
|
163 |
|
| 164 |
ADCdual01A module has several digital data output formats. Difference between these modes lays in the number of differential pairs used.
|
164 |
ADCdual01A module has several digital data output formats. Difference between these modes lays in the number of differential pairs used.
|
| 165 |
|
165 |
|
| 166 |
\begitems
|
166 |
\begitems
|
| 167 |
* 1-lane mode
|
167 |
* 1-lane mode
|
| 168 |
* 2-lane mode
|
168 |
* 2-lane mode
|
| 169 |
* 4-lane mode
|
169 |
* 4-lane mode
|
| 170 |
\enditems
|
170 |
\enditems
|
| 171 |
|
171 |
|
| 172 |
All of the above-mentioned modes are supported by the module design. For the discussed data acquisition system, the 1-lane mode was selected. 1-lane mode allows a minimal number of differential pairs between ADCdual01A and FPGA. Digital signalling scheme used in 1-lane mode is shown in the following image \ref[1-line-out].
|
172 |
All of the above-mentioned modes are supported by the module design. For the discussed data acquisition system, the 1-lane mode was selected. 1-lane mode allows a minimal number of differential pairs between ADCdual01A and FPGA. Digital signalling scheme used in 1-lane mode is shown in the following image \ref[1-line-out].
|
| 173 |
|
173 |
|
| 174 |
\midinsert
|
174 |
\midinsert
|
| 175 |
\clabel[1-line-out]{Single line ADC output signals}
|
175 |
\clabel[1-line-out]{Single line ADC output signals}
|
| 176 |
\picw=15cm \cinspic ./img/ADC_single_line_output.png
|
176 |
\picw=15cm \cinspic ./img/ADC_single_line_output.png
|
| 177 |
\caption/f Digital signalling schema for 1-line ADC digital output mode.
|
177 |
\caption/f Digital signalling schema for 1-line ADC digital output mode.
|
| 178 |
\endinsert
|
178 |
\endinsert
|
| 179 |
|
179 |
|
| 180 |
ADCdual01A parameters can be set either by jumper setup (referred to as a parallel programming in the device's data sheet) or by SPI interface. SPI interface has been selected for our system, because of the parallel programming lack of options (test pattern output setup for example).
|
180 |
ADCdual01A parameters can be set either by jumper setup (referred to as a parallel programming in the device's data sheet) or by SPI interface. SPI interface has been selected for our system, because of the parallel programming lack of options (test pattern output setup for example).
|
| 181 |
|
181 |
|
| 182 |
Complete schematic diagram of ADCdual01A module board is included in the appendix.
|
182 |
Complete schematic diagram of ADCdual01A module board is included in the appendix.
|
| 183 |
|
183 |
|
| 184 |
|
184 |
|
| 185 |
\secc ADC modules interface
|
185 |
\secc ADC modules interface
|
| 186 |
|
186 |
|
| 187 |
\midinsert
|
187 |
\midinsert
|
| 188 |
\picw=10cm \cinspic ./img/FMC2DIFF_top.png
|
188 |
\picw=10cm \cinspic ./img/FMC2DIFF_top.png
|
| 189 |
\picw=10cm \cinspic ./img/FMC2DIFF_Bottom.png
|
189 |
\picw=10cm \cinspic ./img/FMC2DIFF_Bottom.png
|
| 190 |
\caption/f Modelled prewievs of designed and realised PCB of FMC2DIFF01A module.
|
190 |
\caption/f Modelled prewievs of designed and realised PCB of FMC2DIFF01A module.
|
| 191 |
\endinsert
|
191 |
\endinsert
|
| 192 |
|
192 |
|
| 193 |
Both of the ADCdual01A modules were connected to FPGA ML605 board trough FMC2DIFF01A adapter board. The design of this adapter expects the presence of FMC LPC connector on host side and the board is, at the same time, not compatible with MLAB. It is, on the other hand, designed to meet the VITA 57 standard specifications for boards which support region 1 and region 3. VITA 57 regions are explained in the picture \ref[VITA57-regions].
|
193 |
Both of the ADCdual01A modules were connected to FPGA ML605 board trough FMC2DIFF01A adapter board. The design of this adapter expects the presence of FMC LPC connector on host side and the board is, at the same time, not compatible with MLAB. It is, on the other hand, designed to meet the VITA 57 standard specifications for boards which support region 1 and region 3. VITA 57 regions are explained in the picture \ref[VITA57-regions].
|
| 194 |
This industry standard guarantees the compatibility with other FPGA boards that have FMC LPC connectors for Mezzanine Card. Schematic diagram of designed adapter board is included in the appendix.
|
194 |
This industry standard guarantees the compatibility with other FPGA boards that have FMC LPC connectors for Mezzanine Card. Schematic diagram of designed adapter board is included in the appendix.
|
| 195 |
|
195 |
|
| 196 |
The primary purpose of the PCB is to enable the connection of ADC modules located outside the PC case with ML605 development board. (In PC box analog circuits cannot be realized without the use of massive RFI mitigation techniques).
|
196 |
The primary purpose of the PCB is to enable the connection of ADC modules located outside the PC case with ML605 development board. (In PC box analog circuits cannot be realized without the use of massive RFI mitigation techniques).
|
| 197 |
Differential signaling connectors should be used for conducting digital signal over relatively long cables. The signal integrity sensitive links (clocks) are equipped with output driver and translator to LVPECL logic for better signal transmission quality.
|
197 |
Differential signaling connectors should be used for conducting digital signal over relatively long cables. The signal integrity sensitive links (clocks) are equipped with output driver and translator to LVPECL logic for better signal transmission quality.
|
| 198 |
|
198 |
|
| 199 |
LVPECL level signal connectors on FMC2DIFF01A board are dedicated for clock signals. We selected the SY55855V and SY55857L dual translators. Dual configuration in useful due to fact that SATA cable contains two differential pairs.
|
199 |
LVPECL level signal connectors on FMC2DIFF01A board are dedicated for clock signals. We selected the SY55855V and SY55857L dual translators. Dual configuration in useful due to fact that SATA cable contains two differential pairs.
|
| 200 |
|
200 |
|
| 201 |
The SY55855V is a fully differential, CML/PECL/LVPECL-to-LVDS translator. It achieves LVDS signaling up to 1.5Gbps, depending on the distance and the characteristics of the media and noise coupling sources.
|
201 |
The SY55855V is a fully differential, CML/PECL/LVPECL-to-LVDS translator. It achieves LVDS signaling up to 1.5Gbps, depending on the distance and the characteristics of the media and noise coupling sources.
|
| 202 |
LVDS is intended to drive 50 $\Omega$ impedance transmission
|
202 |
LVDS is intended to drive 50 $\Omega$ impedance transmission
|
| 203 |
line media such as PCB traces, backplanes, or cables. SY55855V inputs can be terminated with a single resistor between the true and the complement pins of a given input \cite[SY55855V-chip].
|
203 |
line media such as PCB traces, backplanes, or cables. SY55855V inputs can be terminated with a single resistor between the true and the complement pins of a given input \cite[SY55855V-chip].
|
| 204 |
|
204 |
|
| 205 |
The SY55857L is a fully differential, high-speed dual translator optimized to accept any logic standard from single-ended TTL/CMOS to differential LVDS, HSTL, or CML and translate it to LVPECL. Translation is guaranteed for speeds up to 2.5Gbps (2.5GHz toggle frequency). The SY55857L does not internally terminate its inputs, as different interfacing standards have different termination requirements\cite[SY55857L-chip].
|
205 |
The SY55857L is a fully differential, high-speed dual translator optimized to accept any logic standard from single-ended TTL/CMOS to differential LVDS, HSTL, or CML and translate it to LVPECL. Translation is guaranteed for speeds up to 2.5Gbps (2.5GHz toggle frequency). The SY55857L does not internally terminate its inputs, as different interfacing standards have different termination requirements\cite[SY55857L-chip].
|
| 206 |
|
206 |
|
| 207 |
Inputs of both used chips are terminated accordingly to used logic. The LVDS input is terminated differentially by 100 $\Omega$ resistor between positive and negative inputs. PECL input is terminated by Thevenin resistor network. Thevenin termination method was selected as optimal due to absence of proper power voltage (1,3 V) for direct termination by 50 $\Omega$ resistors. Termination on FPGA side is realized directly by settings proper digital logic type on input pins.
|
207 |
Inputs of both used chips are terminated accordingly to used logic. The LVDS input is terminated differentially by 100 $\Omega$ resistor between positive and negative inputs. PECL input is terminated by Thevenin resistor network. Thevenin termination method was selected as optimal due to absence of proper power voltage (1,3 V) for direct termination by 50 $\Omega$ resistors. Termination on FPGA side is realized directly by settings proper digital logic type on input pins.
|
| 208 |
|
208 |
|
| 209 |
\midinsert
|
209 |
\midinsert
|
| 210 |
\clabel[ML605-development-board]{ML605 development board}
|
210 |
\clabel[ML605-development-board]{ML605 development board}
|
| 211 |
\picw=10cm \cinspic ./img/ML605-board.jpg
|
211 |
\picw=10cm \cinspic ./img/ML605-board.jpg
|
| 212 |
\caption/f FPGA ML605 development board.
|
212 |
\caption/f FPGA ML605 development board.
|
| 213 |
\endinsert
|
213 |
\endinsert
|
| 214 |
|
214 |
|
| 215 |
\midinsert
|
215 |
\midinsert
|
| 216 |
\clabel[VITA57-regions]{VITA57 board geometry}
|
216 |
\clabel[VITA57-regions]{VITA57 board geometry}
|
| 217 |
\picw=10cm \cinspic ./img/VITA57_regions.png
|
217 |
\picw=10cm \cinspic ./img/VITA57_regions.png
|
| 218 |
\caption/f Definition of VITA57 regions.
|
218 |
\caption/f Definition of VITA57 regions.
|
| 219 |
\endinsert
|
219 |
\endinsert
|
| 220 |
|
220 |
|
| 221 |
% doplnit presny pocet konektoru
|
221 |
% doplnit presny pocet konektoru
|
| 222 |
|
222 |
|
| 223 |
Several SATA connectors and two miniSAS connectors are populated on this board. This set of connectors allows a connection of any number of ADC modules within the range of 1 to 8. ADC data outputs should be connected to the miniSAS connectors, while other supporting signals should be routed directly to SATA connectors on adapter.
|
223 |
Several SATA connectors and two miniSAS connectors are populated on this board. This set of connectors allows a connection of any number of ADC modules within the range of 1 to 8. ADC data outputs should be connected to the miniSAS connectors, while other supporting signals should be routed directly to SATA connectors on adapter.
|
| 224 |
|
224 |
|
| 225 |
Lengths of differential pairs routed on PCB of the module are not matched between the pairs. Length variation of differential pairs is not critical in our design according to facts discussed in paragraph \ref[diff-signaling]. Nevertheless, signals within differential pairs themselves are matched for length. Internal signal trace length matching of differential pairs is mandatory in order to minimize jitter and avoid a dynamic logic hazard conditions on digital signals in worst case. Thus clocks signals are routed in the most precise way on all designed boards.
|
225 |
Lengths of differential pairs routed on PCB of the module are not matched between the pairs. Length variation of differential pairs is not critical in our design according to facts discussed in paragraph \ref[diff-signaling]. Nevertheless, signals within differential pairs themselves are matched for length. Internal signal trace length matching of differential pairs is mandatory in order to minimize jitter and avoid a dynamic logic hazard conditions on digital signals in worst case. Thus clocks signals are routed in the most precise way on all designed boards.
|
| 226 |
|
226 |
|
| 227 |
Signal configuration used in our trial design is described in the following tables \ref[minisas-interface], \ref[SPI-system] and \ref[clock-interconnections].
|
227 |
Signal configuration used in our trial design is described in the following tables \ref[minisas-interface], \ref[SPI-system] and \ref[clock-interconnections].
|
| 228 |
|
228 |
|
| 229 |
|
229 |
|
| 230 |
\midinsert \clabel[minisas-interface]{miniSAS differential pairs connections}
|
230 |
\midinsert \clabel[minisas-interface]{miniSAS differential pairs connections}
|
| 231 |
\ctable {cccc}
|
231 |
\ctable {cccc}
|
| 232 |
{
|
232 |
{
|
| 233 |
miniSAS & SATA pair & FMC signal & Used as \cr
|
233 |
miniSAS & SATA pair & FMC signal & Used as \cr
|
| 234 |
P0 & 1 & LA03 & not used \cr
|
234 |
P0 & 1 & LA03 & not used \cr
|
| 235 |
P0 & 2 & LA04 & not used \cr
|
235 |
P0 & 2 & LA04 & not used \cr
|
| 236 |
P1 & 1 & LA08 & not used \cr
|
236 |
P1 & 1 & LA08 & not used \cr
|
| 237 |
P1 & 2 & LA07 & not used \cr
|
237 |
P1 & 2 & LA07 & not used \cr
|
| 238 |
P2 & 1 & LA16 & ADC1 CH1 (LTC2190) \cr
|
238 |
P2 & 1 & LA16 & ADC1 CH1 (LTC2190) \cr
|
| 239 |
P2 & 2 & LA11 & ADC1 CH2 (LTC2190) \cr
|
239 |
P2 & 2 & LA11 & ADC1 CH2 (LTC2190) \cr
|
| 240 |
P3 & 1 & LA17 & ADC2 CH1 (LTC2271) \cr
|
240 |
P3 & 1 & LA17 & ADC2 CH1 (LTC2271) \cr
|
| 241 |
P3 & 2 & LA15 & ADC2 CH2 (LTC2271) \cr
|
241 |
P3 & 2 & LA15 & ADC2 CH2 (LTC2271) \cr
|
| 242 |
}
|
242 |
}
|
| 243 |
\caption/t miniSAS (FMC2DIFF01A J7) signal connections between modules.
|
243 |
\caption/t miniSAS (FMC2DIFF01A J7) signal connections between modules.
|
| 244 |
\endinsert
|
244 |
\endinsert
|
| 245 |
|
245 |
|
| 246 |
|
246 |
|
| 247 |
\midinsert \clabel[SPI-system]{SPI configuration interface connections}
|
247 |
\midinsert \clabel[SPI-system]{SPI configuration interface connections}
|
| 248 |
\ctable {ccc}
|
248 |
\ctable {ccc}
|
| 249 |
{
|
249 |
{
|
| 250 |
SPI connection J7 & FMC signal & Connected to \cr
|
250 |
SPI connection J7 & FMC signal & Connected to \cr
|
| 251 |
SAS-AUX1 & LA14\_N & SPI DOUT \cr
|
251 |
SAS-AUX1 & LA14\_N & SPI DOUT \cr
|
| 252 |
SAS-AUX2 & LA14\_P & SPI CLK \cr
|
252 |
SAS-AUX2 & LA14\_P & SPI CLK \cr
|
| 253 |
SAS-AUX3 & LA12\_N & CE ADC1 \cr
|
253 |
SAS-AUX3 & LA12\_N & CE ADC1 \cr
|
| 254 |
SAS-AUX4 & LA12\_P & CE ADC2 \cr
|
254 |
SAS-AUX4 & LA12\_P & CE ADC2 \cr
|
| 255 |
SAS-AUX5 & LA13\_N & soldered to GND \cr
|
255 |
SAS-AUX5 & LA13\_N & soldered to GND \cr
|
| 256 |
SAS-AUX6 & LA13\_P & not used \cr
|
256 |
SAS-AUX6 & LA13\_P & not used \cr
|
| 257 |
SAS-AUX7 & LA09\_N & not used \cr
|
257 |
SAS-AUX7 & LA09\_N & not used \cr
|
| 258 |
SAS-AUX8 & LA09\_P & soldered to GND \cr
|
258 |
SAS-AUX8 & LA09\_P & soldered to GND \cr
|
| 259 |
}
|
259 |
}
|
| 260 |
\caption/t SPI system interconnections
|
260 |
\caption/t SPI system interconnections
|
| 261 |
\endinsert
|
261 |
\endinsert
|
| 262 |
|
262 |
|
| 263 |
SPI interface is used in an unusual way in this design. SPI Data outputs from ADCs are not connected anywhere and read back is not possible, thus the configuration written to registers in ADC module cannot be validated. We have not observed any problems with this system, but it may be a possible source of failures.
|
263 |
SPI interface is used in an unusual way in this design. SPI Data outputs from ADCs are not connected anywhere and read back is not possible, thus the configuration written to registers in ADC module cannot be validated. We have not observed any problems with this system, but it may be a possible source of failures.
|
| 264 |
|
264 |
|
| 265 |
|
265 |
|
| 266 |
\midinsert \clabel[clock-interconnections]{System clock interconnections}
|
266 |
\midinsert \clabel[clock-interconnections]{System clock interconnections}
|
| 267 |
\ctable {lccc}
|
267 |
\ctable {lccc}
|
| 268 |
{
|
268 |
{
|
| 269 |
Signal & FMC signal & FMC2DIFF01A & ADCdual01A \cr
|
269 |
Signal & FMC signal & FMC2DIFF01A & ADCdual01A \cr
|
| 270 |
DCO & CLK1\_M2C & J5-1 & J13-1 \cr
|
270 |
DCO & CLK1\_M2C & J5-1 & J13-1 \cr
|
| 271 |
FR & LA18\_CC & J10-1 & J12-1 \cr
|
271 |
FR & LA18\_CC & J10-1 & J12-1 \cr
|
| 272 |
ENC & LA01\_CC & J2-1(PECL OUT) & J3-1 \cr
|
272 |
ENC & LA01\_CC & J2-1(PECL OUT) & J3-1 \cr
|
| 273 |
SDGPSDO01A LO & CLK0\_M2C & J3-1 (PECL IN) & N/A \cr
|
273 |
SDGPSDO01A LO & CLK0\_M2C & J3-1 (PECL IN) & N/A \cr
|
| 274 |
}
|
274 |
}
|
| 275 |
\caption/t Clock system interconnections
|
275 |
\caption/t Clock system interconnections
|
| 276 |
\endinsert
|
276 |
\endinsert
|
| 277 |
|
277 |
|
| 278 |
\secc FPGA function
|
278 |
\secc FPGA function
|
| 279 |
|
279 |
|
| 280 |
Several tasks in separate FPGA blocks are performed by FPGA. In first block FPGA prepares sampling clock for ADCdual01A modules by division of main local oscillator. This task is separate block in FPGA and runs asynchronously to other logical circuits. Second block is SPI configuration module, which sends configuration words to ADC modules it is activated by opening of Xillybus interface file. Third block represents the main module, which resolves ADC - PC communication itself it communicates via PCIe, collect data from ADC hardware and creates data packet \ref[xillybus-interface]. Last block is activated after ADC configuration via SPI.
|
280 |
Several tasks in separate FPGA blocks are performed by FPGA. In first block FPGA prepares sampling clock for ADCdual01A modules by division of main local oscillator. This task is separate block in FPGA and runs asynchronously to other logical circuits. Second block is SPI configuration module, which sends configuration words to ADC modules it is activated by opening of Xillybus interface file. Third block represents the main module, which resolves ADC - PC communication itself it communicates via PCIe, collect data from ADC hardware and creates data packet \ref[xillybus-interface]. Last block is activated after ADC configuration via SPI.
|
| 281 |
|
281 |
|
| 282 |
Communication over PCIe is managed by proprietary IP Core and Xillybus driver, which transfers data from FPGA registers to host PC. Data appear in system device file named "/dev/xillybus_data2_r" on the host computer. Binary data which appear in this file after its opening are described in the table below \ref[xillybus-interface].
|
282 |
Communication over PCIe is managed by proprietary IP Core and Xillybus driver, which transfers data from FPGA registers to host PC. Data appear in system device file named "/dev/xillybus_data2_r" on the host computer. Binary data which appear in this file after its opening are described in the table below \ref[xillybus-interface].
|
| 283 |
|
283 |
|
| 284 |
\midinsert
|
284 |
\midinsert
|
| 285 |
\typosize[9/11] \def\tabiteml{ }\let\tabitemr=\tabiteml
|
285 |
\def\tabiteml{ }\let\tabitemr=\tabiteml
|
| 286 |
\clabel[xillybus-interface]{Grabber binary output format}
|
286 |
\clabel[xillybus-interface]{Grabber binary output format}
|
| 287 |
\ctable {lccccccccc}{
|
287 |
\ctable {lccccccccc}{
|
| 288 |
\hfil & \multispan9 \hfil 160bit packet \hfil \crl \tskip4pt
|
288 |
\hfil & \multispan9 \hfil 160bit packet \hfil \strut \crl \tskip4pt
|
| 289 |
Data name & FRAME & \multispan2 \hfil ADC1 CH1 \hfil & \multispan2 \hfil ADC1 CH2 \hfil & \multispan2 \hfil ADC2 CH1 \hfil & \multispan2 \hfil ADC2 CH2 \hfil \cr
|
289 |
Data name & FRAME & \multispan2 \hfil ADC1 CH1 \hfil & \multispan2 \hfil ADC1 CH2 \hfil & \multispan2 \hfil ADC2 CH1 \hfil & \multispan2 \hfil ADC2 CH2 \hfil \strut \cr
|
| 290 |
Data type & uint32 & int16 & int16 & int16 & int16 & int16 & int16 & int16 & int16 \cr
|
290 |
Data type & uint32 & int16 & int16 & int16 & int16 & int16 & int16 & int16 & int16 \cr
|
| 291 |
Content & saw signal & $t1$ & $t_{1+1}$ & $t1$ & $t_{1+1}$ & $t1$ & $t_{1+1}$ & $t1$ & $t_{1+1}$ \cr
|
291 |
Content & saw signal & $t1$ & $t_{1+1}$ & $t1$ & $t_{1+1}$ & $t1$ & $t_{1+1}$ & $t1$ & $t_{1+1}$ \cr
|
| 292 |
}
|
292 |
}
|
| 293 |
\caption/t System device "/dev/xillybus_data2_r" data format
|
293 |
\caption/t System device "/dev/xillybus_data2_r" data format
|
| 294 |
\endinsert
|
294 |
\endinsert
|
| 295 |
|
295 |
|
| 296 |
Data packet block which is carried on PCI Express is described by table \ref[xillybus-interface]. The data packet consist several 32bit words. First word contain FRAME number and it is filled by saw signal for now, with increment step of every data packet transmission. Following data words contains samples from ADCs for first and second channel. Samples from every channel is transmitted in pairs of two samples. Number of ADC channels is expandable according to number of physically connected channels. An CRC word may be added in future at end of transmission packet for data integrity validation.
|
296 |
Data packet block which is carried on PCI Express is described by table \ref[xillybus-interface]. The data packet consist several 32bit words. First word contain FRAME number and it is filled by saw signal for now, with increment step of every data packet transmission. Following data words contains samples from ADCs for first and second channel. Samples from every channel is transmitted in pairs of two samples. Number of ADC channels is expandable according to number of physically connected channels. An CRC word may be added in future at end of transmission packet for data integrity validation.
|
| 297 |
|
297 |
|
| 298 |
FRAME word at beginning of data packet now filled with incrementing and overflowing saw signal is used for ensure that no data samples ale lost during data transfers from FPGA. FRAME signal may be used in future for pairing the ADC samples data packet with another data packet in future. This new additional data packet should carry meta-data information about sample time jitter, current accuracy of local oscillator frequency etc.
|
298 |
FRAME word at beginning of data packet now filled with incrementing and overflowing saw signal is used for ensure that no data samples ale lost during data transfers from FPGA. FRAME signal may be used in future for pairing the ADC samples data packet with another data packet in future. This new additional data packet should carry meta-data information about sample time jitter, current accuracy of local oscillator frequency etc.
|
| 299 |
|
299 |
|
| 300 |
Detailed description of currently implemented FPGA functions can be found in separate paper \cite[fpga-middleware]. HDL source codes for FPGA at state which was used are included on enclosed CD. Future development versions are publicly available from MLAB sources repository.
|
300 |
Detailed description of currently implemented FPGA functions can be found in separate paper \cite[fpga-middleware]. HDL source codes for FPGA at state which was used are included on enclosed CD. Future development versions are publicly available from MLAB sources repository.
|
| 301 |
|
301 |
|
| 302 |
% doplnit odkaz na mlab repozitar
|
302 |
% doplnit odkaz na mlab repozitar
|
| 303 |
|
303 |
|
| 304 |
\secc Data reading and recording
|
304 |
\secc Data reading and recording
|
| 305 |
|
305 |
|
| 306 |
In order to read the data stream from the ADC drive, we use Gnuradio software. Gnuradio suite consists of gnuradio-companion package which is a graphical tool for creating signal-flow graphs and generating Python flow-graph source code. This tool was used to create a basic RAW data grabber to record and interactively view waterfall plots the data streams output from ADC modules.
|
306 |
In order to read the data stream from the ADC drive, we use Gnuradio software. Gnuradio suite consists of gnuradio-companion package which is a graphical tool for creating signal-flow graphs and generating Python flow-graph source code. This tool was used to create a basic RAW data grabber to record and interactively view waterfall plots the data streams output from ADC modules.
|
| 307 |
|
307 |
|
| 308 |
\midinsert
|
308 |
\midinsert
|
| - |
|
309 |
\clabel[grabber-flow-graph]{Gnuradio flow graph for signal grabbing}
|
| 309 |
\picw=15cm \cinspic ./img/screenshots/Grabber.grc.png
|
310 |
\picw=\pdfpagewidth \setbox0=\hbox{\inspic ./img/screenshots/Grabber.grc.png }
|
| - |
|
311 |
\par\nobreak \vskip\wd0 \vskip-\ht0
|
| - |
|
312 |
\centerline {\kern\ht0 \pdfsave\pdfrotate{90}\rlap{\box0}\pdfrestore}
|
| 310 |
\caption/f An ADC recorder flow graph created in gnuradio-companion.
|
313 |
\caption/f The ADC recorder flow graph created in gnuradio-companion.
|
| 311 |
\endinsert
|
314 |
\endinsert
|
| 312 |
|
315 |
|
| 313 |
\midinsert
|
316 |
\midinsert
|
| 314 |
\picw=15cm \cinspic ./img/screenshots/Grabber_running.png
|
317 |
\picw=15cm \cinspic ./img/screenshots/Grabber_running.png
|
| 315 |
\caption/f User interface window of a running ADC grabber.
|
318 |
\caption/f User interface window of a running ADC grabber.
|
| 316 |
\endinsert
|
319 |
\endinsert
|
| 317 |
|
320 |
|
| 318 |
The interactive grabber-viewer user interface shows live oscilloscope-like time-value display for all data channels and live time-frequency scrolling display (a waterfall view) for displaying the frequency components of the grabbed signal. Signal is grabbed to file with exactly the same format, as it is described in table \ref[xillybus-interface].
|
321 |
The interactive grabber-viewer user interface shows live oscilloscope-like time-value display for all data channels and live time-frequency scrolling display (a waterfall view) for displaying the frequency components of the grabbed signal. Signal is grabbed to file with exactly the same format, as it is described in table \ref[xillybus-interface].
|
| 319 |
|
322 |
|
| 320 |
|
323 |
|
| 321 |
\sec Achieved parameters
|
324 |
\sec Achieved parameters
|
| 322 |
|
325 |
|
| - |
|
326 |
Trial design construction was tested for proper handling of sampling rates in range of 5 MSPS to 15 MSPS it should work above this limit. System works on i7 8 cores computer with Ubuntu 12.04 LTS operating system. Data recording of input signal is impossible above sampling rates around 7 MSPS due to bottleneck at HDD speed limits, it should be resolved by use of SSD disk drive. But it is not tested in our setup.
|
| - |
|
327 |
|
| 323 |
\secc ADC module parameters
|
328 |
\secc ADC module parameters
|
| 324 |
|
329 |
|
| 325 |
Two prototypes of ADC modules were assembled and tested. The first prototype, labeled ADC1, has LTC2190 ADC chip populated with LT6600-5 front-end operational amplifier. It also has a 1kOhm resistors populated on inputs which give it an ability of an internal attenuation of the input signal. The value of this attenuation $A$ is described by the following formula \ref[ADC1-gain]
|
330 |
Two prototypes of ADC modules were assembled and tested. The first prototype, labeled ADC1, has LTC2190 ADC chip populated with LT6600-5 front-end operational amplifier. It also has a 1kOhm resistors populated on inputs which give it an ability of an internal attenuation of the input signal. The value of this attenuation $A$ is described by the following formula \ref[ADC1-gain]
|
| 326 |
|
331 |
|
| 327 |
|
- |
|
| 328 |
\label[ADC1-gain]
|
332 |
\label[ADC1-gain]
|
| 329 |
$$
|
333 |
$$
|
| 330 |
A = {806 \cdot R_1 \over R_1 + R_2} \eqmark
|
334 |
A = {806 \cdot R_1 \over R_1 + R_2} \eqmark
|
| 331 |
$$
|
335 |
$$
|
| 332 |
|
336 |
|
| 333 |
Where the letters stand for:
|
337 |
Where the letters stand for:
|
| 334 |
\begitems
|
338 |
\begitems
|
| 335 |
* $A$ - Gain of an input amplifier.
|
339 |
* $A$ - Gain of an input amplifier.
|
| 336 |
* $R_1$ - Output impedance of signal source (usually 50 Ohm).
|
340 |
* $R_1$ - Output impedance of signal source (usually 50 Ohm).
|
| 337 |
* $R_2$ - Value of serial resistors at operational amplifier inputs.
|
341 |
* $R_2$ - Value of serial resistors at operational amplifier inputs.
|
| 338 |
\enditems
|
342 |
\enditems
|
| 339 |
|
343 |
|
| 340 |
We have $R_2 = 1000 \Omega$ and $R_1 = 50 \Omega$ which imply that $A = 0.815$. That value of A is further confirmed by the measurement.
|
344 |
We have $R_2 = 1000 \Omega$ and $R_1 = 50 \Omega$ which imply that $A = 0.815$. That value of A is further confirmed by the measurement.
|
| 341 |
In our measurement setup we have H1012 Ethernet transformer connected to inputs of ADC. The transformer has a 10\% tolerance in impedance and amplification. We measured ADC saturation voltage of 705.7 mV (generator output) in this setup due to impedance mismatch and uncalibrated transformer gain.
|
345 |
In our measurement setup we have H1012 Ethernet transformer connected to inputs of ADC. We have used this transformer for signal symetrization from BNC connector at Agilent 33220A signal generator. Circuit diagram of used transformer circuit is shown in picture and circuit realization in photograph \ref[SMA2SATA-nest].
|
| 342 |
|
346 |
|
| - |
|
347 |
% doplnit schema zapojeni transformatoru.
|
| - |
|
348 |
|
| - |
|
349 |
Used signal generator Agilent 33220A has not optimal parameters for this type of dynamic range measurement. Signal distortion and spurious levels are only -70 dBc according to Agilent datasheet \cite[33220A-generator]. Although, we measured ADC saturation voltage of 705.7 mV (generator output) in this setup due to impedance mismatch and uncalibrated measurement setup and 1V ADC range selected by sense pin. This is relatively high error, but main result from this measurement is FFT plot shown in image \ref[ADC1-FFT], which confirms $>$80 dB dynamic range at ADC module input.
|
| 343 |
|
350 |
|
| 344 |
\midinsert
|
351 |
\midinsert
|
| 345 |
\clabel[ADC1-FFT]{ADC1 sine test FFT}
|
352 |
\clabel[ADC1-FFT]{ADC1 sine test FFT}
|
| 346 |
\picw=15cm \cinspic ./img/screenshots/ADC1_CH2_FFT.png
|
353 |
\picw=15cm \cinspic ./img/screenshots/ADC1_CH2_FFT.png
|
| 347 |
\caption/f Sine signal sampled by ADC1 module with LTC2190 and LT6600-5 devices.
|
354 |
\caption/f Sine signal sampled by ADC1 module with LTC2190 and LT6600-5 devices.
|
| 348 |
\endinsert
|
355 |
\endinsert
|
| 349 |
|
356 |
|
| 350 |
|
357 |
|
| 351 |
For ADC2 we have to use formula with a different constant \ref[ADC1-gain]. The ADC2 module has LT6600-2.5 amplifiers populated on it with gain equal to $A = 2.457$ and uses the same $R_2$ resistors. We measured saturation voltage of 380 mV (generator output) at channel 1 on this ADC. It is well in parameter tolerances of used setup.
|
358 |
Similar test we performed at ADC2 module. For ADC2 we have to use formula with a different constant \ref[ADC1-gain]. The ADC2 module has LT6600-2.5 amplifiers populated on it with gain equal to $A = 2.457$ and uses the same $R_2$ resistors. We measured saturation voltage of 380 mV (generator output) at channel 1 on this ADC. It is well in parameter tolerances of used setup.
|
| 352 |
|
359 |
|
| 353 |
\label[ADC2-gain]
|
360 |
\label[ADC2-gain]
|
| 354 |
$$
|
361 |
$$
|
| 355 |
A = {1580 \cdot R_1 \over R_1 + R_2} \eqmark
|
362 |
A = {1580 \cdot R_1 \over R_1 + R_2} \eqmark
|
| 356 |
$$
|
363 |
$$
|
| 357 |
|
364 |
|
| 358 |
Where the letters stand for:
|
365 |
Where the letters stand for:
|
| 359 |
\begitems
|
366 |
\begitems
|
| 360 |
* $A$ - Gain of an input amplifier.
|
367 |
* $A$ - Gain of an input amplifier.
|
| 361 |
* $R_1$ - Output impedance of signal source (usually 50 Ohm).
|
368 |
* $R_1$ - Output impedance of signal source (usually 50 Ohm).
|
| 362 |
* $R_2$ - Value of serial resistors at operational amplifier inputs.
|
369 |
* $R_2$ - Value of serial resistors at operational amplifier inputs.
|
| 363 |
\enditems
|
370 |
\enditems
|
| 364 |
|
371 |
|
| 365 |
\midinsert
|
372 |
\midinsert
|
| 366 |
\clabel[ADC2-FFT]{ADC2 sine test FFT}
|
373 |
\clabel[ADC2-FFT]{ADC2 sine test FFT}
|
| 367 |
\picw=15cm \cinspic ./img/screenshots/ADC2_CH1_FFT.png
|
374 |
\picw=15cm \cinspic ./img/screenshots/ADC2_CH1_FFT.png
|
| 368 |
\caption/f Sine signal sampled by ADC2 module with LTC2271 and LT6600-2.5 devices.
|
375 |
\caption/f Sine signal sampled by ADC2 module with LTC2271 and LT6600-2.5 devices.
|
| 369 |
\endinsert
|
376 |
\endinsert
|
| 370 |
|
377 |
|
| 371 |
Computed FFT spectra for measured signal are shown in the images \ref[ADC2-FFT] and \ref[ADC1-FFT]. Both images confirm that ADCdual01A modules have input dynamical range of 80 dB at least.
|
378 |
Computed FFT spectra for measured signal are shown in the images \ref[ADC2-FFT] and \ref[ADC1-FFT]. Both images confirm that ADCdual01A modules have input dynamical range of 80 dB at least.
|
| 372 |
|
379 |
|
| - |
|
380 |
\midinsert
|
| - |
|
381 |
\clabel[SMA2SATA-nest]{Used balun transformer}
|
| - |
|
382 |
\picw=15cm \cinspic ./img/SMA2SATA_nest1.JPG
|
| - |
|
383 |
\caption/f Balun transformer circuit used for ADC parameters measurement. It is constructed from H1012 transformer salvaged from an old Ethernet card.
|
| - |
|
384 |
\endinsert
|
| - |
|
385 |
|
| - |
|
386 |
|
| - |
|
387 |
|
| 373 |
\chap Example of usage
|
388 |
\chap Example of usage
|
| 374 |
|
389 |
|
| 375 |
For additional validation of system characteristics a receiver setup has been constructed.
|
390 |
For additional validation of system characteristics a receiver setup has been constructed.
|
| 376 |
|
391 |
|
| 377 |
\sec Basic interferometric station
|
392 |
\sec Basic interferometric station
|
| 378 |
|
393 |
|
| 379 |
Interferometry station was chosen to serve as the most basic experimental setup. We connected the new data acquisition system to two SDRX01B receivers. Block schematics of the setup used is shown in image \ref[block-schematic]. Two ground-plane antennae were used and mounted outside the balcony at CTU building at location 50$^\circ$ 4' 36.102'' N, 14$^\circ$ 25' 4.170'' E.
|
394 |
Interferometry station was chosen to serve as the most basic experimental setup. We connected the new data acquisition system to two SDRX01B receivers. Block schematics of the setup used is shown in image \ref[block-schematic]. Two ground-plane antennae were used and mounted outside the balcony at CTU building at location 50$^\circ$ 4' 36.102'' N, 14$^\circ$ 25' 4.170'' E.
|
| 380 |
Antennae were equipped by LNA01A amplifiers. All coaxial cables have the same length of 5 meters. Antennae were isolated by common mode ferrite bead mounted on cable to minimise the signal coupling between antennas. Evaluation system consists of SDGPSDO local oscillator subsystem used to tune the local oscillator frequency.
|
395 |
Antennae were equipped by LNA01A amplifiers. All coaxial cables have the same length of 5 meters. Antennae were isolated by common mode ferrite bead mounted on cable to minimise the signal coupling between antennas. Evaluation system consists of SDGPSDO local oscillator subsystem used to tune the local oscillator frequency.
|
| 381 |
|
396 |
|
| 382 |
\midinsert
|
397 |
\midinsert
|
| 383 |
\clabel[block-schematic]{Receiver block schematic}
|
398 |
\clabel[block-schematic]{Receiver block schematic}
|
| 384 |
\picw=10cm \cinspic ./img/Coherent_UHF_SDR_receiver.png
|
399 |
\picw=\pdfpagewidth \setbox0=\hbox{\inspic ./img/Coherent_UHF_SDR_receiver.png }
|
| - |
|
400 |
\par\nobreak \vskip\wd0 \vskip-\ht0
|
| - |
|
401 |
\centerline {\kern\ht0 \pdfsave\pdfrotate{90}\rlap{\box0}\pdfrestore}
|
| 385 |
\caption/f Complete receiver block schematic of dual antenna interferometric station.
|
402 |
\caption/f Complete receiver block schematic of dual antenna interferometric station.
|
| 386 |
\endinsert
|
403 |
\endinsert
|
| 387 |
|
404 |
|
| 388 |
% doplnit schema skutecne pouziteho systemu
|
405 |
% doplnit schema skutecne pouziteho systemu
|
| 389 |
|
406 |
|
| 390 |
Despite of schematic diagram proposed on beginning of system description....
|
407 |
Despite of schematic diagram proposed on beginning of system description....
|
| 391 |
We used two separate oscillators -- one oscillator drives encode signal to ADCs still through FPGA based divider and other one drives SDRX01B mixer.
|
408 |
We used two separate oscillators -- one oscillator drives encode signal to ADCs still through FPGA based divider and other one drives SDRX01B mixer.
|
| 392 |
Reason for this modification is simplification of frequency tuning during experiment. It is because single oscillator may be used only with proper setting of FPGA divider, this divider may be modified only by recompilation of FPGA code and loading/flashing new FPGA schema. Due to fact that FPGA was connected to PCI express and kernel drivers and hardware must be reinitialized, reboot of PC is required. Instead of this procedure, we set the FPGA divider to constant division of factor 30 and used another district oscillator for ADCdual01 sampling modules and for SDRX01B receiver.
|
409 |
Reason for this modification is simplification of frequency tuning during experiment. It is because single oscillator may be used only with proper setting of FPGA divider, this divider may be modified only by recompilation of FPGA code and loading/flashing new FPGA schema. Due to fact that FPGA was connected to PCI express and kernel drivers and hardware must be reinitialized, reboot of PC is required. Instead of this procedure, we set the FPGA divider to constant division of factor 30 and used another district oscillator for ADCdual01 sampling modules and for SDRX01B receiver.
|
| 393 |
We use ACOUNT02A MLAB instrument for frequency checking of correct setup on both local oscillators.
|
410 |
We use ACOUNT02A MLAB instrument for frequency checking of correct setup on both local oscillators.
|
| 394 |
|
411 |
|
| 395 |
\midinsert
|
412 |
\midinsert
|
| 396 |
\clabel[meteor-reflection]{Meteor reflection}
|
413 |
\clabel[meteor-reflection]{Meteor reflection}
|
| 397 |
\picw=10cm \cinspic ./img/screenshots/observed_meteor.png
|
414 |
\picw=10cm \cinspic ./img/screenshots/observed_meteor.png
|
| 398 |
\caption/f Meteor reflection received by evaluation setup.
|
415 |
\caption/f Meteor reflection received by evaluation setup.
|
| 399 |
\endinsert
|
416 |
\endinsert
|
| 400 |
|
417 |
|
| 401 |
\midinsert
|
418 |
\midinsert
|
| 402 |
\clabel[phase-difference]{Phase difference}
|
419 |
\clabel[phase-difference]{Phase difference}
|
| 403 |
\picw=10cm \cinspic ./img/screenshots/phase_difference.png
|
420 |
\picw=10cm \cinspic ./img/screenshots/phase_difference.png
|
| 404 |
\caption/f Demonstration of phase difference between antennas.
|
421 |
\caption/f Demonstration of phase difference between antennas.
|
| 405 |
\endinsert
|
422 |
\endinsert
|
| 406 |
|
423 |
|
| 407 |
For simplest demonstration of phase difference between antennas, we analyse part of signal by complex conjugate multiplication between channels. Result of this analysis can be seen on picture \ref[phase-difference]. Points of selected part of signal creates clear vector, which illustrates the presence of phase difference.
|
424 |
For simplest demonstration of phase difference between antennas, we analyse part of signal by complex conjugate multiplication between channels. Result of this analysis can be seen on picture \ref[phase-difference]. Points of selected part of signal creates clear vector, which illustrates the presence of phase difference.
|
| 408 |
|
425 |
|
| 409 |
|
426 |
|
| 410 |
%\sec Simple passive Doppler radar
|
427 |
%\sec Simple passive Doppler radar
|
| 411 |
|
428 |
|
| 412 |
%\sec Simple polarimeter station
|
429 |
%\sec Simple polarimeter station
|
| 413 |
|
430 |
|
| 414 |
\chap Proposed final system
|
431 |
\chap Proposed final system
|
| 415 |
|
432 |
|
| 416 |
Construction of a final system which is supposed to be employed for real radioastronomy observations will be described. This chapter is mainly a theoretical analysis of data handling systems. Realization of these ideas might be possible as a part of our future development after we fully evaluate and test the current trial design.
|
433 |
Construction of a final system which is supposed to be employed for real radioastronomy observations will be described. This chapter is mainly a theoretical analysis of data handling systems. Realization of these ideas might be possible as a part of our future development after we fully evaluate and test the current trial design.
|
| 417 |
|
434 |
|
| 418 |
The system requires proper handling of huge amounts of data and either huge and fast storage capacity is needed for store captured signal data, or enormous computational power is required for online data processing and filtering. Several hardware approach currently exist and are in use for data processing problem handling. Either powerful multi gigahertz CPUs, GPUs, FPGAs, or specially constructed ASICs are used for this task.
|
435 |
The system requires proper handling of huge amounts of data and either huge and fast storage capacity is needed for store captured signal data, or enormous computational power is required for online data processing and filtering. Several hardware approach currently exist and are in use for data processing problem handling. Either powerful multi gigahertz CPUs, GPUs, FPGAs, or specially constructed ASICs are used for this task.
|
| 419 |
|
436 |
|
| 420 |
\sec Custom design of FPGA board
|
437 |
\sec Custom design of FPGA board
|
| 421 |
|
438 |
|
| 422 |
In the beginning of the project, a custom design of FPGA interface board had been considered. This FPGA board should include PCI express interface and should sell at lower price than trial design. It should be compatible with MLAB internal standards which is further backward compatible with the existing or improved design of ADC modules. For a connection of FPGA board to another adapter board with PCIe we expect a use of a PCIe host interface.
|
439 |
In the beginning of the project, a custom design of FPGA interface board had been considered. This FPGA board should include PCI express interface and should sell at lower price than trial design. It should be compatible with MLAB internal standards which is further backward compatible with the existing or improved design of ADC modules. For a connection of FPGA board to another adapter board with PCIe we expect a use of a PCIe host interface.
|
| 423 |
Thunderbolt technology standard was expected to be used in this PC to PCIe module which further communicate with MLAB compatible FPGA module. Thunderbolt chips are currently available on the market for reasonable prices \cite[thunderbolt-chips]. However, a problem lies in the accessibility to their specifications, as specification is only available for licensed users and Intel has a mass market oriented licensing policy, that makes this technology inaccessible for low quantity production. As a consequence, an external PCI Express cabling and expansion slots should be considered as a better solution, if we need preserve standard PC as main computational platform.
|
440 |
Thunderbolt technology standard was expected to be used in this PC to PCIe module which further communicate with MLAB compatible FPGA module. Thunderbolt chips are currently available on the market for reasonable prices \cite[thunderbolt-chips]. However, a problem lies in the accessibility to their specifications, as specification is only available for licensed users and Intel has a mass market oriented licensing policy, that makes this technology inaccessible for low quantity production. As a consequence, an external PCI Express cabling and expansion slots should be considered as a better solution, if we need preserve standard PC as main computational platform.
|
| 424 |
|
441 |
|
| 425 |
However, these PCI express external systems and cables are still very expensive. Take Opal Kelly XEM6110 \cite[fpga-pcie] as an example, with its price tag reaching 995 USD at time of writing of thesis.
|
442 |
However, these PCI express external systems and cables are still very expensive. Take Opal Kelly XEM6110 \cite[fpga-pcie] as an example, with its price tag reaching 995 USD at time of writing of thesis.
|
| 426 |
Therefore, a better solution probably needs to be found.
|
443 |
Therefore, a better solution probably needs to be found.
|
| 427 |
|
444 |
|
| 428 |
An interfacing problem will by probably resolved by other than Intel ix86 architecture. Many ARM computers have risen on market due to increased demand of embedded technologies, which requires high computation capacity, low power consumption and small size -- especially smart phones. Many of those ARM based systems has interesting parameters for signal processing. This facts makes Intel's ix86 architecture unattractive for future project.
|
445 |
An interfacing problem will by probably resolved by other than Intel ix86 architecture. Many ARM computers have risen on market due to increased demand of embedded technologies, which requires high computation capacity, low power consumption and small size -- especially smart phones. Many of those ARM based systems has interesting parameters for signal processing. This facts makes Intel's ix86 architecture unattractive for future project.
|
| 429 |
|
446 |
|
| 430 |
\sec Parralella board computer
|
447 |
\sec Parralella board computer
|
| 431 |
|
448 |
|
| 432 |
Parallella is new product from Adapteva, Inc. \cite[parallella-board], this small supercomputer have been in development almost two years and only testing series of boards have been produced until now (first single-board computers with 16-core Epiphany chip were shipped December 2013) \cite[parallella-board]. This board have near ideal parameters for signal processing (provides around 50 GFLOPS of computational power). The board is equipped by Epiphany coprocessor which has 16 High Performance RISC CPU Cores, Zynq-7020 FPGA with Dual ARM® Cortex™-A9 MPCore™ and 866 MHz operating frequency, 1GB RAM, 85K Logic Cells, 10/100/1000 Ethernet and OpenCL support \cite[parallella16-board]. In addition of that this board consume only 3 Watts of power if both Zynq and Epiphany cores are running.
|
449 |
Parallella is new product from Adapteva, Inc. \cite[parallella-board], this small supercomputer have been in development almost two years and only testing series of boards have been produced until now (first single-board computers with 16-core Epiphany chip were shipped December 2013) \cite[parallella-board]. This board have near ideal parameters for signal processing (provides around 50 GFLOPS of computational power). The board is equipped by Epiphany coprocessor which has 16 High Performance RISC CPU Cores, Zynq-7020 FPGA with Dual ARM® Cortex™-A9 MPCore™ and 866 MHz operating frequency, 1GB RAM, 85K Logic Cells, 10/100/1000 Ethernet and OpenCL support \cite[parallella16-board]. In addition of that this board consume only 3 Watts of power if both Zynq and Epiphany cores are running.
|
| 433 |
|
450 |
|
| 434 |
Main disadvantage of Parralella board is is unknown lead time and absence of SATA interface or other interface for data storage connection. Fast data storage interface would be useful and allows bulk processing of captured data. Then a result from data processing will be sent over the Ethernet interface to data storage server.
|
451 |
Main disadvantage of Parralella board is is unknown lead time and absence of SATA interface or other interface for data storage connection. Fast data storage interface would be useful and allows bulk processing of captured data. Then a result from data processing will be sent over the Ethernet interface to data storage server.
|
| 435 |
|
452 |
|
| 436 |
\midinsert
|
453 |
\midinsert
|
| 437 |
\clabel[img-parallella-board]{Parallella board overview}
|
454 |
\clabel[img-parallella-board]{Parallella board overview}
|
| 438 |
\picw=15cm \cinspic ./img/ParallellaTopView31.png
|
455 |
\picw=15cm \cinspic ./img/ParallellaTopView31.png
|
| 439 |
\caption/f Top view on Parallella-16 board \cite[parallella16-board].
|
456 |
\caption/f Top view on Parallella-16 board \cite[parallella16-board].
|
| 440 |
\endinsert
|
457 |
\endinsert
|
| 441 |
|
458 |
|
| 442 |
If Parallella board will be used as radioastronomy data interface a new ADC interface module should be designed. Interfacing module will use four PEC connectors mounted on bottom of Parallella board. This doughter module should have MLAB compatible design and preferably constructed as separable modules for every Parallella's PEC connectors.
|
459 |
If Parallella board will be used as radioastronomy data interface a new ADC interface module should be designed. Interfacing module will use four PEC connectors mounted on bottom of Parallella board. This doughter module should have MLAB compatible design and preferably constructed as separable modules for every Parallella's PEC connectors.
|
| 443 |
|
460 |
|
| 444 |
\sec GPU based computational system
|
461 |
\sec GPU based computational system
|
| 445 |
|
462 |
|
| 446 |
A new GPU development board NVIDIA K1, shown in the following picture \ref[img-NVIDIA-K1], has recently been released. These boards are intended to be used in fields including computer vision, robotics, medicine, security or automotive industry. They have good parameters for signal processing for a relatively low price of 192 USD. Unfortunately, they are currently only in pre-order release stage (in April 2014).
|
463 |
A new GPU development board NVIDIA K1, shown in the following picture \ref[img-NVIDIA-K1], has recently been released. These boards are intended to be used in fields including computer vision, robotics, medicine, security or automotive industry. They have good parameters for signal processing for a relatively low price of 192 USD. Unfortunately, they are currently only in pre-order release stage (in April 2014).
|
| 447 |
|
464 |
|
| 448 |
\midinsert
|
465 |
\midinsert
|
| 449 |
\clabel[img-NVIDIA-K1]{NVIDIA Jetson TK1 Development Kit}
|
466 |
\clabel[img-NVIDIA-K1]{NVIDIA Jetson TK1 Development Kit}
|
| 450 |
\picw=15cm \cinspic ./img/Jetson_TK1_575px.jpg
|
467 |
\picw=15cm \cinspic ./img/Jetson_TK1_575px.jpg
|
| 451 |
\caption/f The NVIDIA Jetson TK1 Development Kit \url{https://developer.nvidia.com/jetson-tk1}.
|
468 |
\caption/f The NVIDIA Jetson TK1 Development Kit \url{https://developer.nvidia.com/jetson-tk1}.
|
| 452 |
\endinsert
|
469 |
\endinsert
|
| 453 |
|
470 |
|
| - |
|
471 |
NVIDIA board is discrict by presence of PCI Experess connector. This connector should be used for FPGA connection, if we decide to use this development board in our radio astronomy digitalisation system. A new FPGA board with PCI Express direct PCB connector
|
| - |
|
472 |
|
| - |
|
473 |
% doplnit popis pripojeni FPGA desky s HDMI Kabelem.
|
| - |
|
474 |
|
| - |
|
475 |
\sec Other ARM based computation systems
|
| - |
|
476 |
|
| - |
|
477 |
Other embeded ARM based computers for example ODROID-XU, lack of suitable high speed interface. Theirs highest speed interface is USB 3.0 which has currently unsettled development support and needs commercial software tools for evaluation and testing.
|
| - |
|
478 |
|
| - |
|
479 |
|
| - |
|
480 |
From summary analysis mentioned above the Parrallella board should be the best candidate for computational board in radioastronomy data aquisition system. Parralella board is optimised for high data flow processing. Parallella has not much memory to cache processing data but instead of this it has wide bandwidth data channels. Other boards provides much more computational power -- 300 GFLOPS in case of NVIDIA K1, but these boards are optimised for computational heavy tasks on limited amount of data. This is typical problem in computer graphics. But in our application we do not need such extreme computation power at data aquisition system level.
|
| - |
|
481 |
As result we should wait until Parallella becomes widely available. Then new ADCdual interfacing board should be designed ad prepared for use in new scalable radio astronomy data aquisition system. In meen time before suitable computing hardware become accessible. Required applications and algorithms should be optimised on proposed trial design with FPGA development board on standard PC host computer with PCI Express interface to development board.
|
| - |
|
482 |
|